Conclusion and Result of An Etched Ground GCPW 7:1 Unequal Wilkinson Power Divider
The circuits were assembled with SMA end launchers and measured on an Agilent E5071C ENA from 2 – 8 GHz using a short open load through (SOLT) calibration. the simulated and measured results of the power divider, respectively. For the simulated design, the high and low impedance insertion loss values are -8.7 dB and -0.89 dB, respectively. It is believed that the 6 GHz resonance observed in impacts the high impedance insertion loss resulting in a deviation from the ideal value of -9.03 dB. This resonance is due to the asymmetry of the high impedance line. The input return loss is better than -30 dB at 5 GHz while the isolation between high and low impedance sections is approximately -20 dB at 5 GHz.
The measured results show a high and low impedance insertion loss of -9.3 dB and -0.87 dB at 5 GHz. The input return loss is -25 dB and the isolation is better than that at 5 GHz. The measured 3 dB bandwidth defined by the input return loss is calculated to be 10.6 %. The circuits were measured in a round robin fashion by placing a 50 ? load on the port that was not connected to the network analyzer. While making isolation measurements, additional cables were required due to the close proximity of the connectors on the substrate.
As a result a slight ringing noise in the isolation data can be observed. Phase difference comparisons between ports 2 and 3 are shown in. The non-zero phase difference in both results is due to the natural asymmetry of this particular design. Additional efforts could be made to minimize the phase difference such as adding electrical length to the low mpedance side of the power divider.
the insertion loss values and calculated power division ratio for the ideal and the measured “etched ground” GCPW Wilkinson power dividers. Excellent results are achieved with approximately 0.25 dB of connector insertion loss observed in the data at 5 GHz. The calculated power division ratio for the actual structure is 6.93.
A 7:1 unequal Wilkinson power divider has been fabricated in 0.508 mm-thick Rogers RT/Duroid 5880. The measured results indicate a 6.9 power division ratio with isolation and input return loss greater than -20 dB at 5 GHz. A simple etching of the backside ground was used to realize the high impedance sections to achieve this high power division ratio. To the authors’ knowledge, this is the highest unequal Wilkinson power divider published.
Furthermore, by integrating the novel “etched ground” GCPW with the traditional GCPW, impedance values ranging from 30 5 to 230 5 can be realized on the same substrate. This technology has many applications in planar circuits as demonstrated by the unequal Wilkinson power divider and can be extended to double-sided microwave integrated circuit technology (MIC) in a straight forward manner.
Showing posts with label FREE IEEE PAPERS : TOP 100 JANUARY 2015. Show all posts
Showing posts with label FREE IEEE PAPERS : TOP 100 JANUARY 2015. Show all posts
Thursday, March 12, 2015
Cutoff frequency,
defected ground structure (DGS),
effective inductance,
FREE IEEE PAPERS : TOP 100 JANUARY 2015
SOME TEXT FROM PAPER A Novel 1-D Periodic Defected Ground Structure for
Planar Circuits
a measurement and results
The proposed DGS circuit, which is composed of the five-etched lattices. In this letter, we try to compare the measurement results with those of the circular lattice cases, which are described in. Three DGS circuits for measurements have been fabricated using TACONIC CER-10 with 62-mil thick (1.5748 mm) and dielectric constant of 10. The period was kept constant to 5 mm for all three circuits. The etched rectangular area was varied with keeping the square shape. In order to compare the stopband effect of the proposed DGS circuit with previous results, the etched square area was chosen by corresponding to etched circle areas described in.
A line width of 1.46 mm was used, corresponding to 50- line for conventional microstrip line. For smaller square area the cutoff frequency is very high. As the etched area is increased the cutoff frequency becomes lower. Based on previous research, the measured results with constant number of periods show that depth and bandwidth of the stopband depend on the circle radius. In general, the stopband center frequency is a function of the period of the structure. However, the measurements on the proposed DGS circuit show that cutoff frequency and stopband characteristic depend on the etched square dimensions. The period of the proposed DGS defect affects slightly on the stopband center frequency compared with its dimension. The depth and bandwidth of the stopband for the proposed DGS circuit are inclined to depend on the number of period. The etched square area, which determines the effective inductance, characterizes the cutoff and stopband frequency characteristics of the newly proposed DGS structure. The center frequency of stopband for the proposed DGS structure is determined by the resonance frequency of each etched lattice cell. Thus, the cutoff and stopband characteristics for the proposed DGS structure can be easily estimated. Radiation loss could be occurred in some frequency range due to the etched defected area in ground plane. However, addition of the reflected and transmitted power in the first propagation frequency band shows very low radiation level from the ground plane compared with a reported PBG circuits.
a conclusion,
We proposed the novel etched lattice shape for the one-dimensional (1-D) DGS structure. The proposed DGS structure provides the cutoff frequency characteristic due to the effective inductance of the unit lattice, which is etched on microstrip ground plane. The proposed DGS structure is easier to control the cutoff and stopband characteristics by changing the dimensions and to fabricate. And it is much easier than circular periodic cases to analyze proposed periodic structure with finite- difference time-domain (FDTD). It is possible for the newly proposed PBG structure to apply to coplanar waveguide (CPW) and strip line for MMIC applications.
Planar Circuits
a measurement and results
The proposed DGS circuit, which is composed of the five-etched lattices. In this letter, we try to compare the measurement results with those of the circular lattice cases, which are described in. Three DGS circuits for measurements have been fabricated using TACONIC CER-10 with 62-mil thick (1.5748 mm) and dielectric constant of 10. The period was kept constant to 5 mm for all three circuits. The etched rectangular area was varied with keeping the square shape. In order to compare the stopband effect of the proposed DGS circuit with previous results, the etched square area was chosen by corresponding to etched circle areas described in.
A line width of 1.46 mm was used, corresponding to 50- line for conventional microstrip line. For smaller square area the cutoff frequency is very high. As the etched area is increased the cutoff frequency becomes lower. Based on previous research, the measured results with constant number of periods show that depth and bandwidth of the stopband depend on the circle radius. In general, the stopband center frequency is a function of the period of the structure. However, the measurements on the proposed DGS circuit show that cutoff frequency and stopband characteristic depend on the etched square dimensions. The period of the proposed DGS defect affects slightly on the stopband center frequency compared with its dimension. The depth and bandwidth of the stopband for the proposed DGS circuit are inclined to depend on the number of period. The etched square area, which determines the effective inductance, characterizes the cutoff and stopband frequency characteristics of the newly proposed DGS structure. The center frequency of stopband for the proposed DGS structure is determined by the resonance frequency of each etched lattice cell. Thus, the cutoff and stopband characteristics for the proposed DGS structure can be easily estimated. Radiation loss could be occurred in some frequency range due to the etched defected area in ground plane. However, addition of the reflected and transmitted power in the first propagation frequency band shows very low radiation level from the ground plane compared with a reported PBG circuits.
a conclusion,
We proposed the novel etched lattice shape for the one-dimensional (1-D) DGS structure. The proposed DGS structure provides the cutoff frequency characteristic due to the effective inductance of the unit lattice, which is etched on microstrip ground plane. The proposed DGS structure is easier to control the cutoff and stopband characteristics by changing the dimensions and to fabricate. And it is much easier than circular periodic cases to analyze proposed periodic structure with finite- difference time-domain (FDTD). It is possible for the newly proposed PBG structure to apply to coplanar waveguide (CPW) and strip line for MMIC applications.
Wednesday, March 11, 2015
SOME TEXT FROM PAPER One approach to the development of custom SNMP agents and integration with management systems
The proposed SNMP agent is designed using OpenDMK Java libraries. The Project OpenDMK source code is based on the Java Dynamic Management Kit version 5.1 (Java DMK), with the exception of some legacy or deprecated APIs which were removed. OpenDMK provides the necessary tools for integration of Java technology with SNMP Internet network management standard. OpenDMK compatibility with SNMP-based management model enables the development of an agent using the Java programming language, which can be accessed via SNMP protocol [5]. Our SNMP agent developed using this toolkit is completely independent of the SNMP management application installed in the manger station, which allows integration of the developed agent with different management systems. The developed agent is a process that is executed on a managed device that realizes the communication with the managing entity for the purpose of realization management operations. This communication will be later verified by integration of the SNMP agent with two monitoring entities (applications) - Zenoss and Cacti.
In order to test the implemented SNMP agent we performed integration with two network management systems: Zenoss and Cacti. Zenoss is a powerful open source IT monitoring product, while Cacti is an open source, web-based graphing tool designed as a frontend to RRDtool's data storage and graphing functionality.
Since Cacti is only graphing tool, it does not support receiving SNMP trap messages, however it is possible to monitor managed entities using SNMP polling. In order to integrate custom agent with Cacti, it is necessary to define Extensible Markup Language (XML) file that represents a description of MIB table structure. Fig.8 represents XML file that describes MIB table structure for implemented agent.
Because Cacti management system has no support for the acceptance of SNMP Trap it does not provide the ability to fully test the functionality of our implemented agent. Therefore, the SNMP agent has been integrated with another management system, Zenoss. Zenoss provides complete testing of the installed agent, through retrieving/setting the values of managed objects in the MIB and the acceptance of Trap messages. To perform the integration of our agent and management system Zenoss, it is necessary that the MIB, we have designed, is added into the base of non-standard MIB's used by Zenoss, and define the device we want to monitor
The aim of this paper - to explore the possibility of custom agents development and their integration within standard network management systems - has been achieved in the following way. According to the given approach an implementation of one simple SNMP agent using OpenDMK libraries is performed. As is shown in previous chapter, the integration is performed with several network management systems (e.g. Cacti, Zenoss) and tests have confirmed the success of integration. We see future work in researching the possibility of Service Oriented Architecture (SOA) based agents development and their integration within current network management systems.
FCAPS,
FREE IEEE PAPERS : TOP 100 JANUARY 2015,
Network Discovery,
Network Management System,
Network Map,
NMS,
SNMP; MIB,
WANMS,
Web-based Automatic Network discovery/Map Systems
Tuesday, March 10, 2015
Coupled lines with two shorts,
FREE IEEE PAPERS : TOP 100 JANUARY 2015,
high characteristic impedance,
IEEE,
IEEE Explore,
unequal Wilkinson power divider
Some Description of FREE Download IEEE Paper, A 10:1 Unequal Wilkinson Power Divider Using Coupled Lines With Two Shorts
An alternative way to realize an unequal power divider with large dividing ratio can be through using a simple directional coupler. In order to obtain zero phase difference at the output ports, a phase shifter is needed to add to the coupler. This can be realized by using either a piece of transmission line or an integrated wideband phase shifter. The circuit will then either be narrowband in phase response due to presence of the extra transmission line, or become complicated when using the integrated wideband phase shifter. On the other hand, the structure of the directional coupler is more sensitive to the fabrication tolerance, since its dividing ratio is directly determined by coupling
coefficient. In our proposed power divider, however, the coupling coefficient of the coupled line only slightly affects the bandwidth, therefore leading to an easy fabrication.
To avoid the fabrication difficulties, the high characteristic impedance line is realized by using a coupledline section with two shorts. A design example at 2 GHz is fabricated and tested. The measurements agree very well with the simulations. The measured bandwidth of is about 16%. Over this operation bandwidth, the isolation is better than . The measured amplitude balance betweenoutput port 2 and port 3 is between and , and the phase difference is between 0 and 4.6 . The proposed
structure is compatible with single layer integration and easy to design, therefore very attractive for high power dividing ratio applications.
An alternative way to realize an unequal power divider with large dividing ratio can be through using a simple directional coupler. In order to obtain zero phase difference at the output ports, a phase shifter is needed to add to the coupler. This can be realized by using either a piece of transmission line or an integrated wideband phase shifter. The circuit will then either be narrowband in phase response due to presence of the extra transmission line, or become complicated when using the integrated wideband phase shifter. On the other hand, the structure of the directional coupler is more sensitive to the fabrication tolerance, since its dividing ratio is directly determined by coupling
coefficient. In our proposed power divider, however, the coupling coefficient of the coupled line only slightly affects the bandwidth, therefore leading to an easy fabrication.
To avoid the fabrication difficulties, the high characteristic impedance line is realized by using a coupledline section with two shorts. A design example at 2 GHz is fabricated and tested. The measurements agree very well with the simulations. The measured bandwidth of is about 16%. Over this operation bandwidth, the isolation is better than . The measured amplitude balance betweenoutput port 2 and port 3 is between and , and the phase difference is between 0 and 4.6 . The proposed
structure is compatible with single layer integration and easy to design, therefore very attractive for high power dividing ratio applications.
Thursday, March 5, 2015
GET FREE ACCESS DOCUMENT FOR FREE IEEE PAPERS : TOP 100 JANUARY 2015
HOW TO DOWNLOAD : click on the title you want, when there is no paper that can be downloaded, please directly contact us through this page.
HOW TO DOWNLOAD : click on the title you want, when there is no paper that can be downloaded, please directly contact us through this page.
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